FEATURES
DESCRIPTION
APPLICATIONS
DBV PACKAGE (Top View)
SW GND FB
V IN
EN
GND SW V IN
NC EN
FB
3
214
56DRV PACKAGE (Top View)
TYPICAL APPLICATION
L1D1
F
V OUT
V IN to 28 V
V IN
1.8 V to 6.0 V
C 4.7 μ70727476
78808284868890
0.10
110100
E f f i c i e n c y - %
EFFICIENCY
vs
OUTPUT CURRENT
I O - Output Current - mA
TPS61040TPS61041
SLVS413C–OCTOBER 2002–REVISED AUGUST 2007
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LOW-POWER DC/DC BOOST CONVERTER IN SOT-23AND SON PACKAGES
? 1.8-V to 6-V Input Voltage Range
The TPS61040/41is a high-frequency boost converter dedicated for small to medium LCD bias ?Adjustable Output Voltage Range up to 28V supply and white LED backlight supplies.The device ?400-mA (TPS61040)and 250-mA (TPS61041)is ideal to generate output voltages up to 28V from a Internal Switch Current
dual cell NiMH/NiCd or a single cell Li-Ion battery.?Up to 1-MHz Switching Frequency
The part can also be used to generate standard 3.3-V/5-V to 12-V power conversions.
?28-μA Typical No-Load Quiescent Current ?1-μA Typical Shutdown Current The TPS61040/41operates with a switching frequency up to 1MHz.This allows the use of small ?Internal Soft Start
external components using ceramic as well as ?
Available in SOT23-5and 2×2×0.8-mm SON tantalum output capacitors.Together with the thin Packages
SON package,the TPS61040/41gives a very small overall solution size.The TPS61040has an internal 400mA switch current limit,while the TPS61041has ?LCD Bias Supply
a 250-mA switch current limit,offering lower output voltage ripple and allows the use of a smaller form ?White-LED Supply for LCD Backlights factor inductor for lower power applications.The low ?Digital Still Camera
quiescent current (typically 28μA)together with an ?PDAs,Organizers,and Handheld PCs optimized control scheme,allows device operation at ?Cellular Phones
very high efficiencies over the entire load current range.
?Internet Audio Player
?
Standard 3.3-V/5-V to 12-V Conversion
Please be aware that an important notice concerning availability,standard warranty,and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
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VIN
FB
EN
TPS61040TPS61041
SLVS413C–OCTOBER 2002–REVISED AUGUST 2007
These devices have limited built-in ESD protection.The leads should be shorted together or the device placed in conductive foam during storage or handling to prevent electrostatic damage to the MOS gates.
ORDERING INFORMATION
(1)
SWITCH CURRENT
PACKAGE T A
PART NUMBER PACKAGE LIMIT,mA
MARKING TPS61040DBV
400SOT23-5PHOI TPS61041DBV 250SOT23-5PHPI –40°C to 85°C
TPS61040DRV 400SON-62×2CCL TPS61041DRV
250
SON-62×2
CAW
(1)
The devices are available in tape and reel and in tubes.Add R suffix to the part number (e.g.,TPS61040DRVR)to order quantities of 3000parts in tape and reel or add suffix T (e.g.,TPS61040DRVT)to order a tube with 250pieces..
FUNCTIONAL BLOCK DIAGRAM
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DETAILED DESCRIPTION OPERATION
PEAK CURRENT CONTROL
I peak(typ)+I LIM)V IN
L
100ns
I peak(typ)+400mA)V IN
L
100ns for the TPS61040
I peak(typ)+250mA)V IN
L
100ns for the TPS61041
(1)
TPS61040
TPS61041
SLVS413C–OCTOBER2002–REVISED AUGUST2007 Table1.Terminal Functions
TERMINAL
I/O DESCRIPTION
NAME DBV NO.DRV NO.
This is the enable pin of the device.Pulling this pin to ground forces the device into shutdown
EN43I mode reducing the supply current to less than1μA.This pin should not be left floating and needs
to be terminated.
This is the feedback pin of the device.Connect this pin to the external voltage divider to program FB34I
the desired output voltage.
GND21–Ground
NC–5–No connection
Connect the inductor and the Schottky diode to this pin.This is the switch pin and is connected to SW16I
the drain of the internal power MOSFET.
V IN52I Supply voltage pin
The TPS61040/41operates with an input voltage range of1.8V to6V and can generate output voltages up to 28V.The device operates in a pulse-frequency-modulation(PFM)scheme with constant peak current control. This control scheme maintains high efficiency over the entire load current range,and with a switching frequency up to1MHz,the device enables the use of very small external components.
The converter monitors the output voltage,and as soon as the feedback voltage falls below the reference voltage of typically1.233V,the internal switch turns on and the current ramps up.The switch turns off as soon as the inductor current reaches the internally set peak current of typically400mA(TPS61040)or250mA(TPS61041). See the Peak Current Control section for more information.The second criteria that turns off the switch is the maximum on-time of6μs(typical).This is just to limit the maximum on-time of the converter to cover for extreme conditions.As the switch is turned off the external Schottky diode is forward biased delivering the current to the output.The switch remains off for a minimum of400ns(typical),or until the feedback voltage drops below the reference voltage https://www.wendangku.net/doc/db19017238.html,ing this PFM peak current control scheme the converter operates in discontinuous conduction mode(DCM)where the switching frequency depends on the output current,which results in very high efficiency over the entire load current range.This regulation scheme is inherently stable,allowing a wider selection range for the inductor and output capacitor.
The internal switch turns on until the inductor current reaches the typical dc current limit(I LIM)of400mA (TPS61040)or250mA(TPS61042).Due to the internal propagation delay of typical100ns,theactualcurrent exceeds the dc current limit threshold by a small amount.The typical peak current limit can be calculated:
The higher the input voltage and the lower the inductor value,the greater the peak.
By selecting the TPS61040or TPS61041,it is possible to tailor the design to the specific application current limit requirements.A lower current limit supports applications requiring lower output power and allows the use of an inductor with a lower current rating and a smaller form factor.A lower current limit usually has a lower output voltage ripple as well.
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SOFT START
The TPS61040/41limits this inrush current by increasing the current limit in two steps starting from I LIM
4
for 256
cycles to
I LIM
2for the next 256cycles,and then full current limit (see Figure 14).
ENABLE
UNDERVOLTAGE LOCKOUT
ABSOLUTE MAXIMUM RATINGS
DISSIPATION RATING TABLE
TPS61040TPS61041
SLVS413C–OCTOBER 2002–REVISED AUGUST 2007
All inductive step-up converters exhibit high inrush current during start-up if no special precaution is made.This can cause voltage drops at the input rail during start up and may result in an unwanted or early system shut down.
Pulling the enable (EN)to ground shuts down the device reducing the shutdown current to 1μA (typical).Because there is a conductive path from the input to the output through the inductor and Schottky diode,the output voltage is equal to the input voltage during shutdown.The enable pin needs to be terminated and should not be left https://www.wendangku.net/doc/db19017238.html,ing a small external transistor disconnects the input from the output during shutdown as shown in Figure 18.
An undervoltage lockout prevents misoperation of the device at input voltages below typical 1.5V.When the input voltage is below the undervoltage threshold,the main switch is turned off.
over operating free-air temperature (unless otherwise noted)
(1)
UNIT Supply voltages on pin V IN (2)–0.3V to 7V Voltages on pins EN,FB
(2)–0.3V to V IN +0.3V
Switch voltage on pin SW
(2)
30V
Continuous power dissipation See Dissipation Rating Table
T J Operating junction temperature –40°C to 150°C T stg
Storage temperature
–65°C to 150°C
Lead temperature (soldering 10seconds)
260°C
(1)Stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device.These are stress ratings only,and functional operation of the device at these or any other conditions beyond those indicated under recommended operating conditions is not implied.Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.(2)
All voltage values are with respect to network ground terminal.
DERATING T A ≤25°C FACTOR T A =70°C T A =85°C PACKAGE R θJA POWER RATING
ABOVE POWER RATING
POWER RATING
T A =25°C DBV 250°C/W 357mW 3.5mW/°C 192mW 140mW DRV
76°C/W
1300mW
13mW/°C
688mW
500mW
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RECOMMENDED OPERATING CONDITIONS ELECTRICAL CHARACTERISTICS
TPS61040
TPS61041 SLVS413C–OCTOBER2002–REVISED AUGUST2007
MIN TYP MAX UNIT
V IN Input voltage range 1.86V
V OUT Output voltage range28V
L Inductor(1) 2.210μH
f Switchin
g frequency(1)1MHz
C IN Input capacitor(1) 4.7μF
C OUT Output capacitor(1)1μF
T A Operating ambient temperature–4085°C
T J Operating junction temperature–40125°C (1)See application section for further information.
V IN=2.4V,EN=V IN,T A=–40°C to85°C,typical values are at T A=25°C(unless otherwise noted)
PARAMETER TEST CONDITIONS MIN TYP MAX UNIT SUPPLY CURRENT
V IN Input voltage range 1.86V
I Q Operating quiescent current I OUT=0mA,not switching,V FB=1.3V2850μA
I SD Shutdown current EN=GND0.11μA
V UVLO Under-voltage lockout threshold 1.5 1.7V ENABLE
V IH EN high level input voltage 1.3V
V IL EN low level input voltage0.4V
I I EN input leakage current EN=GND or V IN0.11μA POWER SWITCH AND CURRENT LIMIT
Vsw Maximum switch voltage30V
t off Minimum off time250400550ns
t on Maximum on time467.5μs
R DS(on)MOSFET on-resistance V IN=2.4V;I SW=200mA;TPS610406001000m?
R DS(on)MOSFET on-resistance V IN=2.4V;I SW=200mA;TPS610417501250m?MOSFET leakage current V SW=28V110μA
I LIM MOSFET current limit TPS61040350400450mA
I LIM MOSFET current limit TPS61041215250285mA OUTPUT
V OUT Adjustable output voltage range V IN28V
V ref Internal voltage reference 1.233V
I FB Feedback input bias current V FB=1.3V1μA
V FB Feedback trip point voltage 1.8V≤V IN≤6V 1.208 1.233 1.258V
1.8V≤V IN≤6V;V OUT=18V;I load=10mA;
Line regulation(1)0.05%/V
C FF=not connected
Load regulation(1)V IN=2.4V;V OUT=18V;0mA≤I OUT≤30mA0.15%/mA (1)The line and load regulation depend on the external component selection.See the application section for further information.
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TYPICAL CHARACTERISTICS
7072747678808284
8688900.10
110100
E f f i c i e n c y - %
I O - Output Current - mA
7072747678808284
8688900.10
110100
E f f i c i e n c y - %
I L - Load Current - mA
TPS61040TPS61041
SLVS413C–OCTOBER 2002–REVISED AUGUST 2007
Table 2.Table of Graphs
FIGURE
vs Load current 1,2,3ηEfficiency vs Input voltage
4I Q Quiescent current vs Input voltage and temperature 5V FB Feedback voltage vs Temperature 6I SW Switch current limit vs Temperature
7vs Supply voltage,TPS610418I CL Switch current limit vs Supply voltage,TPS610409vs Temperature 10R DS(on)
R DS(on)
vs Supply voltage
11Line transient response 12Load transient response 13Start-up behavior
14
EFFICIENCY
EFFICIENCY
vs
vs
OUTPUT CURRENT
LOAD CURRENT
Figure 1.Figure 2.
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7072747678808284
8688900.10
110100
E f f i c i e n c y - %
I L - Load Current - mA
123456
E f f i c i e n c y - %
V I - Input Voltage - V
- F e e d b a c k V o l t a g e - V
V F B T A - Temperature - °C
Q u i e s c e n t C u r r e n t - A
μV I - Input Voltage - V
TPS61040TPS61041
SLVS413C–OCTOBER 2002–REVISED AUGUST 2007
EFFICIENCY
EFFICIENCY
vs
vs
LOAD CURRENT INPUT VOLTAGE
Figure 3.
Figure 4.
TPS61040
QUIESCENT CURRENT
FEEDBACK VOLTAGE
vs
vs
Figure 5.
Figure 6.
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T A - Temperature - °C
I (S W )- S w i t c h C u r r e n t L i m i t - m A
- C u r r e n t L i m i t - m A
I (C L ) V CC - Supply Voltage - V
?r D S (o n )
? S t a t i c D r a i n -S o u r c e O n -S t a t e R e s i s t a n c e ? m T
A ? Temperature ? °C
- C u r r e n t L i m i t - m A
I (C L ) V CC - Supply Voltage - V
TPS61040TPS61041
SLVS413C–OCTOBER 2002–REVISED AUGUST 2007
TPS61040/41
TPS61041SWITCH CURRENT LIMIT
CURRENT LIMIT
vs
vs
FREE-AIR TEMPERATURE SUPPLY VOLTAGE
Figure 7.Figure 8.
TPS61040TPS61040/41
CURRENT LIMIT
STATIC DRAIN-SOURCE ON-STATE RESISTANCE
vs
vs
SUPPLY VOLTAGE
FREE-AIR TEMPERATURE
Figure 9.
Figure 10.
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V I
2.4 V to
3.4 V
V O
100 mV/div 200 μS/div
V O = 18 V
?
r D S (o n )? S t a t i c D r a i n -S o u r c e O n -S t a t e R e s i s t a n c e ? m V CC ? Supply Voltage ? V
V O 5 V/div EN 1 V/div
I I
50 mA/div
V O = 18 V
V O
1 mA to 10 mA
200 μS/div
V O
100 mA/div
V O = 18 V
TPS61040TPS61041
SLVS413C–OCTOBER 2002–REVISED AUGUST 2007
TPS61040/41
STATIC DRAIN-SOURCE ON-STATE RESISTANCE
vs
Figure 11.
Figure 12.Line Transient Response
Figure 13.Load Transient Tresponse Figure 14.Start-Up Behavior
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APPLICATION INFORMATION
INDUCTOR SELECTION,MAXIMUM LOAD CURRENT
fS max +
V IN(min) (V OUT *V IN)
I P L V OUT (2)
fS ǒ
I load ǔ
+2 I load (V OUT *V IN )Vd)
I 2P L
(3)
I load max +h I 2P L fS max
2 (V OUT *V
IN)(4)
TPS61040TPS61041
SLVS413C–OCTOBER 2002–REVISED AUGUST 2007
Because the PFM peak current control scheme is inherently stable,the inductor value does not affect the stability of the regulator.The selection of the inductor together with the nominal load current,input and output voltage of the application determines the switching frequency of the converter.Depending on the application,inductor values between 2.2μH and 47μH are recommended.The maximum inductor value is determined by the maximum on time of the switch,typically 6μs.The peak current limit of 400mA/250mA (typically)should be reached within this 6-μs period for proper operation.
The inductor value determines the maximum switching frequency of the converter.Therefore,select the inductor value that ensures the maximum switching frequency at the converter maximum load current is not exceeded.The maximum switching frequency is calculated by the following formula:
Where:
I P =Peak current as described in the Peak Current Control section L =Selected inductor value
V IN(min)=The highest switching frequency occurs at the minimum input voltage
If the selected inductor value does not exceed the maximum switching frequency of the converter,the next step
is to calculate the switching frequency at the nominal load current using the following formula:
Where:
I P =Peak current as described in the Peak Current Control section L =Selected inductor value I load =Nominal load current
Vd =Rectifier diode forward voltage (typically 0.3V)
A smaller inductor value gives a higher converter switching frequency,but lowers the efficiency.
The inductor value has less effect on the maximum available load current and is only of secondary order.The
best way to calculate the maximum available load current under certain operating conditions is to estimate the expected converter efficiency at the maximum load current.This number can be taken out of the efficiency graphs shown in Figure 1through Figure 4.The maximum load current can then be estimated as follows:
Where:
I P =Peak current as described in the Peak Current Control section L =Selected inductor value
fS max =Maximum switching frequency as calculated previously η=Expected converter efficiency.Typically 70%to 85%
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SETTING THE OUTPUT VOLTAGE
V OUT+1.233Vǒ1)R1R2ǔ(5)
C FF+1
2p fS
20R1
(6)
TPS61040
TPS61041
SLVS413C–OCTOBER2002–REVISED AUGUST2007
The maximum load current of the conveter is the current at the operation point where the coverter starts to enter the continuous conduction https://www.wendangku.net/doc/db19017238.html,ually the converter should always operate in discontinuous conduction mode.
Last,the selected inductor should have a saturation current that meets the maximum peak current of the converter(as calculated in the Peak Current Control section).Use the maximum value for I LIM for this calculation. Another important inductor parameter is the dc resistance.The lower the dc resistance,the higher the efficiency of the converter.See Table3and the typical applications for the inductor selection.
Table3.Recommended Inductor for Typical LCD Bias Supply(see Figure15)
DEVICE INDUCTOR VALUE COMPONENT SUPPLIER COMMENTS
10μH Sumida CR32-100High efficiency
10μH Sumida CDRH3D16-100High efficiency
TPS6104010μH Murata LQH4C100K04High efficiency
4.7μH Sumida CDRH3D16-4R7Small solution size
4.7μH Murata LQH3C4R7M24Small solution size
High efficiency
TPS6104110μH Murata LQH3C100K24
Small solution size
The output voltage is calculated as:
For battery-powered applications,a high-impedance voltage divider should be used with a typical value for R2of ≤200k?and a maximum value for R1of2.2M?.Smaller values might be used to reduce the noise sensitivity of the feedback pin.
A feedforward capacitor across the upper feedback resistor R1is required to provide sufficient overdrive for the error comparator.Without a feedforward capacitor,or one whose value is too small,the TPS61040/41shows double pulses or a pulse burst instead of single pulses at the switch node(SW),causing higher output voltage ripple.If this higher output voltage ripple is acceptable,the feedforward capacitor can be left out.
The lower the switching frequency of the converter,the larger the feedforward capacitor value required.A good starting point is to use a10-pF feedforward capacitor.As a first estimation,the required value for the feedforward capacitor at the operation point can also be calculated using the following formula:
Where:
R1=Upper resistor of voltage divider
fS=Switching frequency of the converter at the nominal load current(See the INDUCTOR SELECTION, MAXIMUM LOAD CURRENT section for calculating the switching frequency)
C FF=Choose a value that comes closest to the result of the calculation
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OUTPUT CAPACITOR SELECTION
D V out+I out
C outǒ1fS(Iout)–I P L
Vout)Vd–Vinǔ)I P ESR(7)
TPS61040
TPS61041
SLVS413C–OCTOBER2002–REVISED AUGUST2007
The larger the feedforward capacitor the worse the line regulation of the device.Therefore,when concern for line regulation is paramount,the selected feedforward capacitor should be as small as possible.See the LINE AND LOAD REGULATION section for more information about line and load regulation.
The line regulation of the TPS61040/41depends on the voltage ripple on the feedback https://www.wendangku.net/doc/db19017238.html,ually a50mV peak-to-peak voltage ripple on the feedback pin FB gives good results.
Some applications require a very tight line regulation and can only allow a small change in output voltage over a certain input voltage range.If no feedforward capacitor C FF is used across the upper resistor of the voltage feedback divider,the device has the best line regulation.Without the feedforward capacitor the output voltage ripple is higher because the TPS61040/41shows output voltage bursts instead of single pulses on the switch pin (SW),increasing the output voltage ripple.Increasing the output capacitor value reduces the output voltage ripple.
If a larger output capacitor value is not an option,a feedforward capacitor C FF can be used as described in the previous section.The use of a feedforward capacitor increases the amount of voltage ripple present on the feedback pin(FB).The greater the voltage ripple on the feedback pin(≥50mV),the worse the line regulation. There are two ways to improve the line regulation further:
https://www.wendangku.net/doc/db19017238.html,e a smaller inductor value to increase the switching frequency which will lower the output voltage ripple,
as well as the voltage ripple on the feedback pin.
2.Add a small capacitor from the feedback pin(FB)to ground to reduce the voltage ripple on the feedback pin
down to50mV again.As a starting point,the same capacitor value as selected for the feedforward capacitor
C FF can be used.
For best output voltage filtering,a low ESR output capacitor is recommended.Ceramic capacitors have a low ESR value but tantalum capacitors can be used as well,depending on the application.
Assuming the converter does not show double pulses or pulse bursts on the switch node(SW),the output voltage ripple can be calculated as:
where:
I P=Peak current as described in the Peak Current Control section
L=Selected inductor value
I out=Nominal load current
fS(I out)=Switching frequency at the nominal load current as calculated previously
Vd=Rectifier diode forward voltage(typically0.3V)
C out=Selected output capacitor
ESR=Output capacitor ESR value
See Table4and the typical applications section for choosing the output capacitor.
Table4.Recommended Input and Output Capacitors
DEVICE CAPACITOR VOLTAGE RATING COMPONENT SUPPLIER COMMENTS
4.7μF/X5R/0805 6.3V Tayo Yuden JMK212BY475MG C IN/C OUT
10μF/X5R/0805 6.3V Tayo Yuden JMK212BJ106MG C IN/C OUT TPS61040/411μF/X7R/120625V Tayo Yuden TMK316BJ105KL C OUT
1μF/X5R/120635V Tayo Yuden GMK316BJ105KL C OUT
4.7μF/X5R/121025V Tayo Yuden TMK325BJ475MG C OUT
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INPUT CAPACITOR SELECTION
DIODE SELECTION
LAYOUT CONSIDERATIONS
D1
V O
V IN C TPS61040TPS61041
SLVS413C–OCTOBER 2002–REVISED AUGUST 2007
For good input voltage filtering,low ESR ceramic capacitors are recommended.A 4.7μF ceramic input capacitor is sufficient for most of the applications.For better input voltage filtering this value can be increased.See Table 4and typical applications for input capacitor recommendations.
To achieve high efficiency a Schottky diode should be used.The current rating of the diode should meet the peak current rating of the converter as it is calculated in the Peak Current Control https://www.wendangku.net/doc/db19017238.html,e the maximum value for I LIM for this calculation.See Table 5and the typical applications for the selection of the Schottky diode.
Table 5.Recommended Schottky Diode for Typical LCD Bias Supply (see Figure 15)
DEVICE
REVERSE VOLTAGE
COMPONENT SUPPLIER COMMENTS
30V
ON Semiconductor MBR053020V ON Semiconductor MBR0520TPS61040/41
20V ON Semiconductor MBRM120L
High efficiency 30V
Toshiba CRS02
Typical for all switching power supplies,the layout is an important step in the design;especially at high peak currents and switching frequencies.If the layout is not carefully done,the regulator might show noise problems and duty cycle jitter.
The input capacitor should be placed as close as possible to the input pin for good input voltage filtering.The inductor and diode should be placed as close as possible to the switch pin to minimize the noise coupling into other circuits.Because the feedback pin and network is a high-impedance circuit,the feedback network should be routed away from the inductor.The feedback pin and feedback network should be shielded with a ground plane or trace to minimize noise coupling into this circuit.
Wide traces should be used for connections in bold as shown in Figure 15.A star ground connection or ground plane minimizes ground shifts and noise.
Figure https://www.wendangku.net/doc/db19017238.html,yout Diagram
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L1D1
V OUT 18 V
V IN
1.8 V to 6 V
C14.7 μF
L1:Sumida CR32-100D1:Motorola MBR0530
C1:Tayo Yuden JMK212BY475MG C2:
Tayo Yuden TMK316BJ105KL
L1D1
V IN
1.8 V to 6 V
4.7 DAC or Analog Voltage 0 V = 25 V 1.233 V = 18 V Sumida CR32-100Motorola MBR0530
Tayo Yuden JMK212BY475MG C2:
Tayo Yuden GMK316BJ105KL
V OUT
18 V / 10 mA
V IN
1.8 V to 6 V
4.7 μR3200 k W
μF Sumida CR32-100Motorola MBR0530
Tayo Yuden JMK212BY475MG Tayo Yuden TMK316BJ105KL
TPS61040TPS61041
SLVS413C–OCTOBER 2002–REVISED AUGUST 2007
Figure 16.LCD Bias Supply
Figure 17.LCD Bias Supply With Adjustable Output Voltage
Figure 18.LCD Bias Supply With Load Disconnect
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V IN = 2.7 V to 5 V
C1
4.7 μF
V2 = -10 V/15 mA
Murata LQH4C6R8M04
Motorola MBR0530
Tayo Yuden JMK212BY475MG
Tayo Yuden EMK316BJ105KF
L1
D1
μ
F
V O=12 V/35 mA
V IN 3.3 V
10 μL1:Murata LQH4C6R8M04
D1:Motorola MBR0530
C1:Tayo Yuden JMK212BJ106MG
C2:Tayo Yuden EMK316BJ475ML
μF
5 V/45 mA
1.8 V to 4 V
4.7
L1:Murata LQH4C3R3M04
D1:Motorola MBR0530
C1, C2:Tayo Yuden JMK212BY475MG
TPS61040
TPS61041
SLVS413C–OCTOBER2002–REVISED AUGUST2007 Figure19.Positive and Negative Output LCD Bias Supply
Figure20.Standard3.3-V to12-V Supply
Figure21.Dual Battery Cell to5-V/50-mA Conversion
Efficiency Approx.Equals84%at V IN=2.4V to Vo=5V/45mA
Copyright?2002–2007,Texas Instruments Incorporated Submit Documentation Feedback15
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L1V CC
PWM
100 Hz to 500 Hz
L1:Murata LQH4C100K04D1:Motorola MBR0530
C1:Tayo Yuden JMK212BY475MG C2:
Tayo Yuden TMK316BJ105KL
L1D1
MBRM120L
4.7 μV CC = 2.7 V to 6 V
0 V ? Iled = 20 mA
L1:Murata LQH4C3R3M04D1:Motorola MBR0530
C1:Tayo Yuden JMK212BY475MG C2:Standard Ceramic Capacitor
TPS61040TPS61041
SLVS413C–OCTOBER 2002–REVISED AUGUST 2007
Figure 22.White LED Supply With Adjustable Brightness Control
Using a PWM Signal on the Enable Pin,Efficiency Approx.Equals 86%at V IN =3V,I LED =15mA
A.
A smaller output capacitor value for C2causes a larger LED ripple.
Figure 23.White LED Supply With Adjustable Brightness Control
Using an Analog Signal on the Feedback Pin
16Submit Documentation Feedback Copyright ?2002–2007,Texas Instruments Incorporated
PACKAGING INFORMATION
Orderable Device Status (1)Package Type Package Drawing Pins Package Qty Eco Plan (2)
Lead/Ball Finish MSL Peak Temp (3)TPS61040DBVR ACTIVE SOT-23DBV 53000Green (RoHS &
no Sb/Br)CU NIPDAU Level-1-260C-UNLIM TPS61040DBVRG4ACTIVE SOT-23DBV 53000Green (RoHS &
no Sb/Br)CU NIPDAU Level-1-260C-UNLIM TPS61040DRVR PREVIEW SON DRV 63000
TBD
Call TI Call TI
TPS61041DBVR ACTIVE SOT-23DBV 53000Green (RoHS &
no Sb/Br)CU NIPDAU Level-1-260C-UNLIM TPS61041DBVRG4ACTIVE SOT-23DBV 53000Green (RoHS &
no Sb/Br)CU NIPDAU Level-1-260C-UNLIM TPS61041DRVR PREVIEW SON DRV 53000TBD Call TI Call TI TPS61041DRVT
PREVIEW
SON
DRV
5
250
TBD
Call TI
Call TI
(1)
The marketing status values are defined as follows:ACTIVE:Product device recommended for new designs.
LIFEBUY:TI has announced that the device will be discontinued,and a lifetime-buy period is in effect.
NRND:Not recommended for new designs.Device is in production to support existing customers,but TI does not recommend using this part in a new design.
PREVIEW:Device has been announced but is not in production.Samples may or may not be available.OBSOLETE:TI has discontinued the production of the device.
(2)
Eco Plan -The planned eco-friendly classification:Pb-Free (RoHS),Pb-Free (RoHS Exempt),or Green (RoHS &no Sb/Br)-please check https://www.wendangku.net/doc/db19017238.html,/productcontent for the latest availability information and additional product content details.TBD:The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS):TI's terms "Lead-Free"or "Pb-Free"mean semiconductor products that are compatible with the current RoHS requirements for all 6substances,including the requirement that lead not exceed 0.1%by weight in homogeneous materials.Where designed to be soldered at high temperatures,TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt):This component has a RoHS exemption for either 1)lead-based flip-chip solder bumps used between the die and package,or 2)lead-based die adhesive used between the die and leadframe.The component is otherwise considered Pb-Free (RoHS compatible)as defined above.
Green (RoHS &no Sb/Br):TI defines "Green"to mean Pb-Free (RoHS compatible),and free of Bromine (Br)and Antimony (Sb)based flame retardants (Br or
Sb do not exceed 0.1%by weight in homogeneous material)
(3)
MSL,Peak Temp.--The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications,and peak solder temperature.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided.TI bases its knowledge and belief on information provided by third parties,and makes no representation or warranty as to the accuracy of such information.Efforts are underway to better integrate information from third parties.TI has taken and continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.TI and TI suppliers consider certain information to be proprietary,and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s)at issue in this document sold by TI to Customer on an annual basis.
PACKAGE OPTION ADDENDUM
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15-Oct-2007
TAPE AND REEL BOX
INFORMATION
Device
Package Pins Site
Reel Diameter (mm)Reel Width (mm)A0(mm)B0(mm)K0(mm)
P1(mm)W (mm)Pin1Quadrant TPS61040DBVR DBV 5SITE 481798 3.2 3.2 1.448Q3TPS61041DBVR
DBV
5
SITE 48
179
8
3.2
3.2
1.4
4
8
Q3
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5-Oct-2007
Device
Package Pins Site Length (mm)
Width (mm)Height (mm)
TPS61040DBVR DBV 5SITE 48195.0200.045.0TPS61041DBVR
DBV
5
SITE 48
195.0
200.0
45.0
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5-Oct-2007