SD8925G 输入10V-30V输出5V 2.1A同步降压车充IC

8L Packag ble in SOP-e SD8925G e SD8925G 30V, the SD8925G ac G is a sy e SD89254% Efficie

2.1A 10V~30V Wide Range Synchronous Buck Controller

F e a t u r Wide I Up to Progra to up t No Loo Progra Cable Therm Availa A p p l i c a Car Ch Pre-Re Distrib Battery

e

s

Input Voltag 9n ammable Sw to 500kHz op Compen ammable cu Compensat mal Shutdow t i o n s

harger / Ada egulator for buted Power y Charger

e Range: 10ncy witching Freq sation Requ rrent limit tion from 0n aptor Linear Regu r Systems 0V to 30V

quency up uired ? to 0.3? e ulators

Th re Op to ou re pr

sy eff pr sta Th re Ot pr sh Th ind

D e s c r i p t i h gulator from perating with X utput curren gulation.

rogrammable ynchronous ficient des rovides fast t abilization.

h adily availab ther feature rogrammable hutdown.

h dustry stand

o n

n m a high h an input v h nt with exc The switc e from 150 k architecture signs. Curr transient res requires a ble standard es include e current converter dard SOP-8L

nchronous voltage inp voltage rang hieves 2.1A cellent load ching freq kHz to 500 k e provides rent mode sponse and a minimum d external co cable com limit and rs are availa L packages.

step down put supply. e from 10V continuous d and line quency is

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eases loop number of

omponents.mpensation, d thermal

able in the

SD8925G

Shouding

········

····T y p i c a l A p p l i c a t i o n C i r c u i t * The output voltage is set by R2 and R3: V OUT = 1.21V ? [1 + (R2/R3)].

The SD8925G is guaranteed to meet

P i n A s s i g n m e n t

a n d D e s c r i p t i o n

A b s o l u t e M a x i m u m R a t i n g s (N o t e 1)

Input Supply Voltage ....................................................................................................-0.3V

～ 35V FB, ILIM, RT Voltages.................................................................................................... -0.3V ～ 6V SW Voltage ........................................................................................................-0.3V ～ (VIN + 1V) Operating Temperature Range (Note 2)………...………………………………………-40℃ ～ +85℃

Storage Temperature Range.................................................................................. -65℃ ～ +150℃ Junction Temperature Range………………………………………………...……………..……...+150℃ Lead Temperature (Soldering, 10 sec.).................................................................................. +265℃ Note 1: Stresses beyond those listed Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime. Note 2: performance specifications from 0℃ to 70℃. Specifications over the –40℃

to 85℃ operating temperature range are assured by design, characterization and correlation with statistical process controls.

PIN

NAME

DESCRIPTION 1 FB Feedback

2 RT Frequency Setting

3 ILIM Current Limit

4 VIN Input Supply Voltage

5, 6 SW Switch Node

7, 8

GND

Ground

····

···Main Supply Pin. The SD8925G operates from P i n F u n c t i o n s FB (Pin 1): Feedback Pin. Receive the feedback voltage from an external resistive divider across the output. In the adjustable version, the output voltage is fixed. The Output voltage is set by R2 and R3: V OUT = 1.21V ? [1 + (R2/R3)].

RT (Pin 2): The internal oscillator is set with a single resistor between this pin and the GND pin. ILIM (Pin 3): Monitors current through the low-side switch and triggers current limit operation if the inductor valley current exceeds a user defined value that is set by R LIM and the Sense current sourced out of this pin during operation.

VIN (Pin 4): 10V to 30V unregulated input. It must be closely decoupled to GND, with a 47μF or greater ceramic capacitor to prevent large voltage spikes

from appearing at the input.

SW (Pin 5, 6):

Switch Node Connection to Inductor. GND (Pin 7, 8): Ground Pin.

E l e c t r i c a l C h a r a c t e r i s t i c s

Operating Conditions: T A=25, V

℃IN=12V, R2=470k, R3=150k, unless otherwise specified.

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS V IN Operating Voltage Range 10 30 V

I Q Quiescent

Current I LOAD

=0A 10

15

20

mA

I SHDN Shutdown

Current 110 150 μA V UVLO Input UVLO Threshold 4.25 4.5 V

ΔV UVLO UVLO

Hysteresis 50 100

mV V FB Regulated

Voltage 1.188 1.21 1.236 V

I FB Feedback Pin Input Current0.05 μA

f OSC Oscillator Frequency Range

150 500 kHz

R T

=100k 180 220 260 kHz DC Max Duty Cycle 100 %

I LIM-TH Current Limit Sense Pin

Source Current 7 8.5 10 μA

R PFET R DS(ON) of P-Channel FET 65 m?R NFET R DS(ON) of N-Channel FET 30 m?T SD Thermal Shutdown Temperature

Rising 125 ℃

ΔT SD Thermal Shutdown

Hysteresis 30

℃

T y p i c a l P e r f o r m a n c e C h a r a c t e r i s t i c s

Operating Conditions: T A=25℃, C IN=47μF, C OUT=100μF, L=10μH, unless otherwise noted.

Vin=24V

Vin=12V

B l o c k D i a g r a

m

The SD8925G oscillator frequency is set by a single Continuously running the SD8925G The total power dissipation in SD8925G is limited The SD8925G operates by a

A p p l i c a t i o n I n f o r m a t i o n

constant frequency, current mode architecture. The output voltage is set by an external divider returned to the FB pin. An error amplifier compares the divided output voltage with a reference voltage of 1.21V and adjusts the peak inductor current accordingly.

During normal operation, the internal P-channel MOSFET is turned on each cycle when the oscillator sets the RS latch, and turned off when the current comparator, resets the RS latch. While the P-channel MOSFET is off, the N-channel MOSFET is turned on until either the inductor current starts to reverse, as indicated by the current reversal comparator or the beginning of the next clock cycle. Thermal Protection

by a thermal protection circuit. When the device temperature rises to approximately 125℃, this circuit turns off the output, allowing the IC to cool. The thermal protection circuit can protect the device from being damaged by overheating in the event of fault conditions. into thermal shutdown degrades device reliability. Current Limit

Current limit detection occurs during the off-time by monitoring the current through the low-side switch using an external resistor, R LIM . The current limit value is defined by R LIM . If during the off-time the current in the low-side switch exceeds the user defined current limit value, the next on-time cycle is immediately terminated. Current sensing is achieved by comparing the voltage across the low side FET with the voltage across the current limit set resistor R LIM . For example, the current limit value is 2.1A by the R LIM =62k. The current limit value rises when the set resistor R LIM rises. The maximum output current is set by R LIM : R LIM (k ?) = 24? I MAX (A). Oscillator Frequency

external resistor connected between the RT pin and the GND pin. The resistor should be located very close to the device and connected directly to the pins of the IC (RT and GND). An internal amplifier holds the RT pin at a fixed voltage typically 0.6V. The oscillator frequency rises when the resistor R T falls. To determine the timing resistance for a given switching frequency, use the equation below:

R T (k ?)= 22000 /f OSC (kHz)

Setting Output Voltage

The output voltage is set with a resistor divider from the output node to the FB pin. It is recommended to use divider resistors with 1% tolerance or better. To improve efficiency at very light loads consider using larger value resistors. If the values are too high the regulator is more susceptible to noise and voltage errors from the FB input current are noticeable. For most applications, a resistor in the 10k ? to 1M ? range is suggested for R3. R2 is then given by:

R2 = R3 ? [(V OUT / V REF ) – 1]

where V REF is 1.21V.

ments than on what the SD8925G requires to operate.

able, the SD8925G integrates a

Output Cable Resistance Compensation

To compensate for resistive voltage drop across the charger's output c simple, user-programmable cable voltage drop compensation using the impedance at the FB pin. Choose the proper feedback resistance values for cable compensation refer to the curve in Figure 1. The delta VOUT voltage rises when the feedback resistance R3 value rises. The delta VOUT voltage rises when the feedback resistance R3 value rises, use the equation below:

ΔV OUT (V) = R3(k ?) ? I OUT (A)/635

Figure 1. Delta Output Voltage vs. Load Current

Inductor Selection

For most applications, the value of the inductor will fall in the range of 4.7μH to 47μH. Its value is chosen based on the desired ripple current. Large value inductors lower ripple current and small value inductors result in higher ripple currents. Higher V IN or V OUT also increases the ripple current as shown in equation. A reasonable starting point for setting ripple current is I △L =840mA (40% of 2.1A).

The DC current rating of the inductor should be at least equal to the maximum load current plus half the ripple current to prevent core saturation. Thus, a 2.94A rated inductor should be enough for most applications (2.1A + 840mA). For better efficiency, choose a low DC-resistance inductor.

Different core materials and shapes will change the size/current and price/current relationship of an inductor. Toroid or shielded pot cores in ferrite or perm alloy materials are small and don’t radiate much energy, but generally cost more than powdered iron core inductors with similar electrical characteristics. The choice of which style inductor to use often depends more on the price vs. size requirements and any radiated field/EMI require

Output and Input Capacitor Selection

In continuous mode, the source current of the top MOSFET is a square wave of duty cycle V OUT/V IN. To prevent large voltage transients, a low ESR input capacitor sized for the maximum RMS current must be

used. The maximum RMS capacitor current is given by:

This formula has a maximum at V IN = 2V OUT, where I RMS = I OUT/2. This simple worst-case condition is

commonly used for design because even significant deviations do not offer much relief. Note that the

capacitor manufacturer’s ripple current ratings are often based on 2000 hours of life. This makes it

advisable to further derate the capacitor, or choose a capacitor rated at a higher temperature than

required. Always consult the manufacturer if there is any question.

The selection of C OUT is driven by the required effective series resistance (ESR).Typically, once the

ESR requirement for C OUT has been met, the RMS current rating generally far exceeds the I RIPPLE(P-P)

requirement. The output ripple ΔV OUT is determined by:

Where f = operating frequency, C OUT = output capacitance and ΔI L = ripple current in the inductor. For a

fixed output voltage, the output ripple is highest at maximum input voltage since ΔI L increases with input

voltage.

Aluminum electrolytic and dry tantalum capacitors are both available in surface mount configurations. In

the case of tantalum, it is critical that the capacitors are surge tested for use in switching power supplies.

An excellent choice is the AVX TPS series of surface mount tantalum. These are specially constructed

and tested for low ESR so they give the lowest ESR for a given volume.

Efficiency Considerations

The efficiency of a switching regulator is equal to the output power divided by the input power times

100%. It is often useful to analyze individual losses to determine what is limiting the efficiency and which

change would produce the most improvement. Efficiency can be expressed as: Efficiency = 100% - (L1+

L2+ L3+ ...) where L1, L2, etc. are the individual losses as a percentage of input power. Although all

dissipative elements in the circuit produce losses, two main sources usually account for most of the

losses: VIN quiescent current and I2R losses. The VIN quiescent current loss dominates the efficiency

loss at very low load currents whereas the I2R loss dominates the efficiency loss at medium to high load

currents. In a typical efficiency plot, the efficiency curve at very low load currents can be misleading

since the actual power lost is of no consequence.

1. The VIN quiescent current is due to two components: the DC bias current as given in the electrical

characteristics and the internal main switch and synchronous switch gate charge currents. The gate

charge current results from switching the gate capacitance of the internal power MOSFET switches.

Each time the gate is switched from high to low to high again, a packet of charge ΔQ moves from VIN to

ground. The resulting ΔQ/Δt is the current out of VIN that is typically larger than the DC bias current.

operation of the SD8925G. Check

In continuous mode, I GATECHG = f (Q T +Q B ) where Q T and Q B are the gate charges of the internal top and bottom switches. Both the DC bias and gate charge losses are proportional to VIN and thus their effects will be more pronounced at higher supply voltages.

2. I 2R losses are calculated from the resistances of the internal switches, R SW and external inductor R L . In continuous mode the average output current flowing through inductor L is “chopped” between the main switch and the synchronous switch. Thus, the series resistance looking into the SW pin is a function of both top and bottom MOSFET R DS(ON) and the duty cycle (DC) as follows: R SW = R DS(ON)TOP x DC + R DS(ON)BOT x (1-DC) The R DS(ON) for both the top and bottom MOSFETs can be obtained from the Typical Performance Characteristics curves. Thus, to obtain I 2R losses, simply add R SW to R L and multiply the result by the square of the average output current. Other losses including C IN and C OUT ESR dissipative losses and inductor core losses generally account for less than 2% of the total loss.Board Layout Suggestions

When laying out the printed circuit board, the following checklist should be used to ensure proper the following in your layout.

1. The power traces, consisting of the GND trace, the SW trace and the VIN trace should be kept

short, direct and wide. 2. Put the input capacitor as close as possible to the device pins (VIN and GND).

3. SW node is with high frequency voltage swing and should be kept small area. Keep analog

components away from SW node to prevent stray capacitive noise pick-up. 4. Connect all analog grounds to a command node and then connect the command node to the power

ground behind the output capacitors.

SOP-8L Package Outline Dimension

NS6316规格书,3A车充IC方案,可限流

NS63164-30V 输入3A 输出同步降压稳压器 1特性 ●宽输入电压范围：4V 至30V ●宽输出电压范围：1.8V 至28V ●效率可高达92%以上●超高恒流精度：±5%●恒压精度：±2%●无需外部补偿 ●开关频率：130kHz ●输入欠压/过压、输出短路和过热保护●SOP-8封装● 输出电流：3A 2应用范围 ●车载充电器/适配器●线性调节前置稳压器●分布式供电系统● 电池充电器 3说明 NS6316是支持高电压输入的同步降压电源管理芯片，在4~30V 的宽输入电压范围内可实现3A 的连续电流输出。通过调节FB 端口的分压电阻，可以输出1.8V 到28V 的稳定电压。NS6316具有优秀的恒压/恒流(CC/C)特性。NS6316采用电流模式的环路控制原理，实现了快速的动态响应。NS6316工作开关频率为130kHz ，具有良好的EMI 特性。 NS6316内置线电压补偿，可通过调节FB 端口的分压电阻阻值来实现。NS6316不仅可实现单芯片降压电源管理方案，还可以与QC2.0/QC3.0识别芯片构成快速充电电源管理方案。另外，芯片包含多重保护功能：过温保护，输出短路保护和输入欠压/过压保护等。 NS6316采用SOP8的标准封装。4典型应用电路 NS6316方案PCB和原理图： https://www.wendangku.net/doc/6011883578.html,/product/NS6316-274.html 。

SOP-8的管脚图如下图所示： 6极限工作参数 ●VIN 电压-0.3V ~33V ●FB 电压-0.3V ~33V ●SW 电压-0.3V ~33V ●CSN 电压-0.3V ~33V ●CSP 电压-0.3V ~33V ●工作温度范围-40℃~+85℃●存储温度范围-55℃~+150℃ ●结温范围 +150℃● 焊接温度（10s 内） +265℃ 注1：超过上述极限工作参数范围可能导致芯片永久性的损坏。长时间暴露在上述任何极限条件下可能会影响芯片的可靠性和寿命。 注2：NS6316可以在0℃到70℃的限定范围内保证正常的工作状态。超过-40℃至85℃温度范围的工作状态受设计和工艺控制影响。 编号管脚名称管脚描述管脚功能 1 FB 反馈输入 该管脚用于检测并设定输出电压；输出电压大小由R1和R2设定：V OUT =1.0V×[1+(R1/R2)]2CSN 输出电压 输出电压脚 3CSP 电流采样脚 该管脚用于检测并设定输出恒流值；输出恒流值大小由R3设定：Icc=Vcc_ref/R3 4VIN 电源供电管脚，该管脚应接至少100uF 电解电容到地，以避免输入端在工作时出现较大的电压波动 5,6 SW 功率开关输出端 该管脚为开关节点，与电感连接，用于负载功率输出 7,8GND 地接地管脚

5V2A,3A车充IC,AT2601

Approved By Test By Miller Lin 深圳市天芯源电子有限公司 https://www.wendangku.net/doc/6011883578.html, AT2601 TEST REPORT Product Model: USB CLA ● Test Status: ■Sample-test ● Input Voltage : 12V / 24V / 32V ● Dual Output Voltage: ● Dual Output Currant: ● The Duration Of Testing: 5V 2.1A 2012. 03. 30 ● Report Issue Date: : 2012. 03. 30

S W Circuit Diagram Dual Output Currant: 2.1A V in C3 C2 C1 R2 Q1 R1 10 4 1 0 0 u F /4 0 V 4 7 u F/4 0 V 51 0 2N39 04 0.12 U1 D1 V g ate Ip k G C1 V in FB G ND 1N41 48 G C2 TC R5 R4 C5 R6 1k 3K C6 10 3 16 0K L1 10 2 RX 10 0uH Vout R3 C4 22 C7 C9 51 0 15 0P D1 22 0uF 10 4 ZD 1 CX 10 2 SS 2 4 5.6V

Efficiency Test Output Ripple Test Output Capacitor 330uF/10V

SD8925G 输入10V-30V输出5V 2.1A同步降压车充IC

8L Packag ble in SOP-e SD8925G e SD8925G 30V, the SD8925G ac G is a sy e SD89254% Efficie 2.1A 10V~30V Wide Range Synchronous Buck Controller F e a t u r Wide I Up to Progra to up t No Loo Progra Cable Therm Availa A p p l i c a Car Ch Pre-Re Distrib Battery e s Input Voltag 9n ammable Sw to 500kHz op Compen ammable cu Compensat mal Shutdow t i o n s harger / Ada egulator for buted Power y Charger e Range: 10ncy witching Freq sation Requ rrent limit tion from 0n aptor Linear Regu r Systems 0V to 30V quency up uired ? to 0.3? e ulators Th re Op to ou re pr sy eff pr sta Th re Ot pr sh Th ind D e s c r i p t i h gulator from perating with X utput curren gulation. rogrammable ynchronous ficient des rovides fast t abilization. h adily availab ther feature rogrammable hutdown. h dustry stand o n n m a high h an input v h nt with exc The switc e from 150 k architecture signs. Curr transient res requires a ble standard es include e current converter dard SOP-8L nchronous voltage inp voltage rang hieves 2.1A cellent load ching freq kHz to 500 k e provides rent mode sponse and a minimum d external co cable com limit and rs are availa L packages. step down put supply. e from 10V continuous d and line quency is kHz and the for highly operation eases loop number of omponents.mpensation, d thermal able in the SD8925G Shouding ········ ····T y p i c a l A p p l i c a t i o n C i r c u i t * The output voltage is set by R2 and R3: V OUT = 1.21V ? [1 + (R2/R3)].

SD8583S电源芯片车充ic方案

SD8583S 说明书 内置高压MOS 管的原边控制开关电源 描述 SD8583S 是内置高压MOS 管功率开关的原边控制开关电源（PSR ），采用PFM 调制技术，提供精确的恒压/恒流（CV/CC ）控制环路，具有非常高的稳定性和平均效率。 采用SD8583S 设计系统，无需光耦，可省去次级反馈控制、环路补偿，精简电路、降低系统成本。 SD8583S 适用8~10W 输出功率，内置线损补偿功能和峰值电流补偿功能。 主要特点 ? 内置高压MOS 管功率开关 ? 原边控制模式 ? 低启动电流 ? 前沿消隐 ? 逐周期限流 ? PFM 调制 ? 降峰值模式 ? 过压保护 ? 欠压锁定 ? 环路开路保护 ? 最大导通时间保护 ? 过温保护 ? 线损电压补偿 ? 峰值电流补偿 应用 ? 充电器 ? 适配器 ? 待机电源 产品规格分类

内部框图 管脚排列图 CDC ISEN Drain Drain 管脚说明 管脚号 管脚名称 I/O 功 能 描 述 1 VCC P 供电电源； 2 FB I 反馈电压输入端； 3 CDC I 输出线损补偿端； 4 ISEN I 峰值电流采样端； 5、6 Drain O 高压MOS 管漏端； 7 GND G 地。

极限参数（除非特殊说明，T amb=25°C） MOS管电气参数（除非特殊说明，T amb=25°C）

电气参数（除非特殊说明，V CC =18V，T amb =25°C）

参数温度特性 -12.0 -8.0-4.0012.0温度(°C)启动电流 (μA ) -40-20 20 40 60 80120 启动电流vs. 温度 温度(°C) 启动电压(V ) 启动电压vs. 温度 温度(°C)关断电压 (V ) 关断电压vs. 温度 温度(°C) 恒压阈值 (V ) 恒压阈值vs. 温度 1008.04.015.0 16.0 17.018.020.021.0-40-20 020********* 1006.0 7.08.09.011.012.0-40-20 20 40 60 80120 100 3.30 3.50 3.90 4.10 4.50-40 -20 0204060 80120 10019.010.0 3.704.30 功能描述 SD8583S 是离线式开关电源集成电路，是内置线损补偿和峰值电流补偿的高端开关电源控制器。通过检测变压器原级线圈的峰值电流和辅助线圈的反馈电压，控制系统的输出电压和电流，达到输出恒压或者恒流的目的。 完整的工作周期分为峰值电流检测和反馈电压检测： 当MOS 管导通，通过采样电阻检测原级线圈的电流，此时FB 端电压为负，输出电容对负载供电，输出电压V O 下降；当原级线圈的电流到达峰值时，MOS 管关断，FB 端电压检测开始。存储在次级线圈的能量对输出电容充电，输出电压V O 上升，并对负载供电。当同时满足恒压、恒流环路控制的开启条件后，MOS 管才开启。随之，芯片再次进入峰值电流检测。 1. 电路启动和欠压锁定 系统上电，电路由高压直流母线通过启动电阻对VCC 管脚外置的电容充电。当VCC 上升到17.8V ，电路开始工作；在电路正常工作过程中，由启动电阻和辅助线圈共同供电来维持VCC 电压；当VCC 下降到8.8V 进入欠压锁定状态，启动电阻对VCC 电容供电，VCC 上升到17.8V ，电路启动重新工作。

AAP6150A双路限流车充IC

AAP6150A 7.5V to 40V Input Supply, Synchronous Buck PWM Controller FEATURES Wide 7.5V to 40V Input Voltage Range Drive Dual Low Cost N-Channel MOSFETs -Adaptive Shoot-Through-Protection High Efficiency Up to 95% 0.8V reference with +/- 1.5% accuracy Fast Load Transient Response Dual Output with Independent Programmable Over-Current Control Over-Current Control Accuracy +/-3% Nearly Zero Input Current at Output Over Current Protection or Output Under- Voltage Protection Internal Soft-Start Programmable Output Cable Compensation 200kHz Fixed Switching Frequency Thermal shutdown Protection Available in MSOP-10 Package RoHS Compliant and Halogen Free APPLICATIONS Car Charger/Adaptor Rechargeable Portable Devices Battery Charger DESCRIPTION The AAP6150A is a voltage mode synchronous buck controller that achieves excellent load and line regulation. The device operates from an input voltage range of 7.5V to 40V.The AAP6150A provides protection functions including: input under-voltage lockout, output under-voltage protection and programmable over-current protection with two independent outputs. The AAP6150A is housed in a MSOP10 Package. ORDERING INFORMATION

IA1219,30V 同步降压IC 车充 DC-DC降压

IA1219 2A 27V Synchronous Buck Converter Description The IA1219 is a monolithic synchronous buck regulator. The device integrates 95 m? MOSFETS that provide 2A continuous load current over a wide operating input voltage of 4.5V to 27V. Current mode control provides fast transient response and cycle-by-cycle current limit. An adjustable soft-start prevents inrush current at turn on. Features 2A Output Current Wide 4.5V to 27V Operating Input Range Integrated Power MOSFET switches Output Adjustable from 0.925V to 0.8Vin Up to 96% Efficiency Programmable Soft-Start Stable with Low ESR Ceramic Output Capacitors Fixed 340KHZ Frequency Cycle-by-Cycle Over Current Protection Short Circuit Protection Input Under Voltage Lockout Package ： SOP-8L Applications Distributed Power Systems Networking Systems FPGA, DSP, ASIC Power Supplies Green Electronics/ Appliances Notebook Computers Typical Application Circuit Michael Chu QQ:1 651316203

USB车充工作原理

34063是一种开关型高效DC/DC 变换集成电路。34063能够控制的开关峰值电流达到0.8-1.5A ；实际最高输出电流为峰值电流60%左右。34063工作原理如下： 1．比较器的反相输入端(脚5)通过外接分压电阻R1、R2监视输出电压 。其中，输出电压Uo=1.25(1+ R2/R1)由公式可知输出电压 。仅与R1、R2数值有关，因1．25V 为基准电压，恒定不变。若R1、R2阻值稳定，U 。亦稳定。 2．脚5电压与内部基准电压1．25V 同时送人内部比较器进行电压比较。当脚5的电压值低于内部基准电压(1．25V)时，比较器输出为跳变电压，开启R —S 触发器的S 脚控制门，R —S 触发器在内部振荡器的驱动下，Q 端为“1”状态(高电平)，驱动管T2导通，开关管T1亦导通，使输入电压Ui 向输出滤波器电容Co 充电以提高U 。，达到自动控制U 。稳定的作用。 3．当脚5的电压值高于内部基准电压(1．25V)时，R —S 触发器的S 脚控制门被封锁，Q 端为“0”状态(低电平)，T2截止，T1亦截止。 4. 振荡器的Ipk 输入(脚7)用于监视开关管T1的峰值电流，以控制振荡器的脉冲输出到R —S 触发器的Q 端。 5. 脚3外接振荡器所需要的定时电容Co 电容值的大小决定振荡器频率的高低，亦决定开关管T1的通断时间。 注释： 1）输出电压计算公式：Uo=1.25*（1+R2/R1）=1.25（1+4.7/1.5）=5.17V R2和R1必须选用1%精密电阻，电压误差±5%左右。 DRC 8 IPK 7 V+ 6 CINV 5 SWC 1 SWE 2 CT 3 V- 4 U1 MC34063 D1 1N5819 R2 1.5K 1/6W R6 4.7K 1/6W R3(2) C1 47uF 35V R4 0．22R 1W C2 470pF C3 220UF 10V L1 100UH J1

LP64920 同步整流车充IC

30V 2.4A Synchronous Buck Converter General Description The LP64920 is a synchronous, rectified, step-down, switch-mode converter with built-in power MOSFET. The LP64920 offers a very compact solution that achieves a maximum of 2.4A of continuous output current. The LP64920 has synchronous mode operation for high efficiency over the output current load range. Current-mode operation provides fast transient response and eases loop stabilization. The LP64920 requires a minimum number of readily available standard external components. Other features include cable compensation, programmable current limit and thermal shutdown. Order Information LP64920 □ □ □ □ F: Pb-Free Package Type SO: SOP8 Current Sense Voltage A: V CS =53mV B: V CS =65mV Applications ? Car Charger ? Pre-Regulator for Linear Regulators ? Distributed Power Systems ? USB Dedicated Charging Ports (DCP) Features ◆ Wide 8V to 30V Continuous Operating Input Range ◆ 78mΩ/65mΩ Low R DS(ON) Internal Power MOSFET ◆ Up to 93% Efficiency ◆ Default 160kHz Switching Frequency ◆ Internal Soft Start ◆ Output Line Drop Compensation ◆ Over-Current Protection (OCP) programmable with External Resistor ◆ No Loop Compensation Required ◆ Thermal Shutdown ◆ Available in SOP8 Package Typical Application Circuit LP64920 ＊＊＊输出带过压保护，不烧手机＊＊＊ 布线要求： １：输入电容尽量靠近ＩＣ输入脚，且输入和输出电容的地尽量靠近ＩＣ地。５：Ｒｕｐ电阻取输出电容或输出电容后面，Ｒｄｎ电阻做单点接地，尽量离７８脚近。 ２：ＦＢ的走线尽量短，且不要有靠近或是经过ＳＷ脚的走线。 ４：带线补后建议在Ｒｄｎ电阻上面并联一个４７ＰＦ电容防干扰。 ３：Ｒｕｐ和Ｒｄｎ的电阻同比例增加线补增加；例：１８０Ｋ／２４Ｋ线补０．３Ｖ。６：ＣＳ的走线远离ＳＷ脚的高频走线，且不要从ＳＷ走线的底层经过。

车充IC车充芯片最低成本方案

n Excellent line and load regulation n TTL shutdown capability n ON/OFF pin with hysteresis function n With output constant current loop n Built in thermal shutdown function n Built in current limit function n Built in output over voltage protection n SOP8-EP (Exposed PAD) package Applications n Car Charger n Battery Charger n LED Constant Current Driver number of external components, the regulator is simple to use and include internal frequency compensation and a fixed-frequency oscillator. The PWM control circuit is able to adjust the duty ratio linearly from 0 to 100%. An enable function, an over current protection function is built inside. An internal compensation block is built in to minimize external component count. Figure1. Package Type of XL4001

大电流车充IC方案XL4501

宽输入电压范围 n输出电压从1.25V到32V可调n最小压差0.3V n固定150KHz开关频率 n最大5A开关电流 n内置功率MOS n出色的线性与负载调整率 n内置恒流环路 n内置频率补偿功能 n内置输出短路保护功能 n内置输入过压保护功能 n内置热关断功能n TO263-5L封装 应用 n车载充电器 n电池充电器 n LCD电视与显示屏 n便携式设备供电 n通讯设备供电 n降压恒流驱动 n显示器LED背光 n通用LED照明 描述 XL4501是一款高效降压型DC-DC转换 器，可工作在DC8V到36V输入电压范围， 低纹波，内置功率MOS。XL4501内置固定 频率振荡器与频率补偿电路，简化了电路设 计。 PWM控制环路可以调节占空比从 0~100%之间线性变化。内置输出过电流保 护功能。内部补偿模块可以减少外围元器件 数量。 图1.XL4501封装

150KHz 36V 5A开关电流自带恒流环路降压型DC-DC转换器XL4501 引脚配置 图2. XL4501引脚配置 表1.引脚说明 引脚号引脚名称引脚描述 1 GND 接地引脚。 2 FB 反馈引脚，通过外部电阻分压网络，检测输出电压进行调整，参考电压为1.25V。 3 SW 功率开关输出引脚，SW是输出功率的开关节点。 4 CS 输出电流检测引脚（IOUT=0.11V/RCS）。 5 VIN 输入电压，支持DC8V~36V宽范围电压操作，需要在VIN与GND 之间并联电解电容以消除噪声。

150KHz 36V 5A开关电流自带恒流环路降压型DC-DC转换器XL4501 方框图 图3. XL4501方框图 典型应用 图4. XL4501系统参数测量电路

JW1610子弹头车充方案5v1a车充ic

一、概述 JW1610是一款单芯片的同步降压调节器。内部集成了100mΩ的MOSFET，在输入电压范围内可持续的提供1A的负载电流，芯片电流控制模块为整个系统提供快速的瞬态响应和逐周期的电流限制。内部集成软启动功能可在系统开启时防止浪涌电流损坏IC。在短路状态下，输入电流低至1uA左右。该IC采用8引脚SOP封装，提供了一个非常紧凑的系统解决方案，最少程度的依赖于外部元件。 二、特点 1A输出电流 宽输入电压范围（6.4V至40V） 内部集成100mΩ的功率MOSFET管 输出电压在从0.925V至20V之间可调 高达90%以上的效率 可编程软启动 固定340KHz的频率 逐周期的过电流保护 输入欠压锁定 8引脚SOP封装 三、产品应用 分布式电源系统网络系统 机顶盒液晶电视/显示器 笔记本 四、引脚图及说明 引脚图序号名称功能描述 SOP-81BS 上管驱动栅极输入端，在BS和SW之间连接一个0.01μF或更大 的电容，充电升压后为上管（N沟道MOSFET）提供驱动电压 2IN 电源输入端。为IC和降压稳压器提供4.75V~18V的电源，在输 入和地之间接一个合适大小的旁路电容，减少输入到IC的噪声3SW 功率开关管输出端。这个开关节点为输出提供能量，将LC滤波 器连接在SW和输出端。注意需要BS和SW之间的升压电容驱 动开关管 4GND芯片地 5FB 反馈输入端。输出端经过电阻分压后提供给FB的输入，通过这 个采样反馈来调节输出电压，反馈端的比较点为0.925V 6COMP 补偿端。在COMP和地之间的串联RC网络被用来补偿系统的闭 环控制，一些情况下需要在COMP和地之间再加一个电容 7EN 使能输入端。稳压器的使能输入端，高电平使能，接100K的上 拉电阻可自动启动。 8SS 软启动控制输入端。SS到地之间的电容大小设置软启动的时间， 当电容值为0.1μF时启动时间约为15mS，若不使用此功能，可 将其悬空。 五、内部框图

LP64930同步整流5V3.6A DCDC车充用IC

L P64930 30V 3.5A Synchronous Buck Converter General Description The LP64930 is a synchronous step down regulator with CC control from a high voltage input supply. Operating with an input voltage 8V~30V, the LP64930 achieves 3.5A continuous output current with excellent load and line regulation. Current mode operation provides fast transient response and eases loop stabilization. The LP64930 requires a minimum number of readily available standard external components. Other features include cable compensation, programmable current limit and thermal shutdown. The LP64930 converters are available in the industry standard SOP8 packages. Order Information LP64930 □ □ □ □ F: Pb-Free Package Type SO: SOP8 Current Sense Voltage A: V CS =53mV B: V CS =65mV Applications ? Car Charger / Adaptor ? Pre-Regulator for Linear Regulators ? Distributed Power Systems ? Battery Charger Features ◆ Wide 8V to 30V Continuous Operating Input Range ◆ 58mΩ/45mΩ Low R DS(ON) Internal Power MOSFET ◆ Up to 93% Efficiency ◆ Default 180kHz Switching Frequency ◆ Internal Soft Start ◆ Output Line Drop Compensation ◆ Over-Current Protection (OCP) programmable with External Resistor ◆ No Loop Compensation Required ◆ Thermal Shutdown ◆ Available in SOP8 Package Typical Application Circuit Marking Information ＊＊＊输出带过压保护，不烧手机＊＊＊

FP6719内置QC3.0协议的车充IC 带QC3.0认证

FP6719 High Efficiency, Synchronous Boost Converter with QC 2.0 Fast Charging Function Pin Assignments SP Package (SOP-8 Exposed Pad) D+OUT EN LX VIN VREG D-HVSS Fig ure 1. Pin Assignment of FP6719 Ordering Information Description The FP6719 is highly-integrated switch-mode system power management devices for smart power bank application and regulated output voltage including 5V /9V /12V. Its low impedance power switch optimizes switch-mode operation efficiency, reduces MOS power consumption. The USB D+/D- data line makes the device protocol handshake to set suitable output voltage to do fast charging function. The chip is compliant with QC 2.0 class A specifications with Max. output current up to 3A at 5V. Besides the converter includes two switch MOSFETs as synchronous boost converter. So no external Schottky diode is required and could get better efficiency near 92%. Other features include built-in soft start, thermal shutdown protection, under-voltage lockout (UVLO), and short circuit protection function, which can shut off the device if output voltage reaches below 1.5V. The FP6719 is available in a space-saving SOP-8 (Exposed Pad ) package with an exposed pad. Features ● Input Voltage Range from 2.9V to 5.5V. ● Output Voltage Can be Set to 5V/9V/12V. ● Built-in Low R DS (ON) Integrated Power MOSFET ● NMOS 39mΩ/PMOS 42mΩ ● 3.0A Output Current at 5V ● Fixed Switching Frequency 400KHz. ● Power-Save Mode for Light-Load Efficiency. ● Short Circuit Current Fold-back Protection. ● Built-in Soft Start, Output Overvoltage Protection and Thermal Protection ● Supports USB DCP Shorting D+ Line to D- Line per USB Battery Charging Specification, Revision 1.2. ● Meets Chinese Telecommunication Industrial Standard YD/T 1591-2009 ● Supports USB DCP applying 2.7V on D+ line and 2.7V on D- line. ● Supports USB DCP applying 1.2V on D+ and D- lines ● Automatic selection of D+/D- mode for an attached device ● Complaint with Apple? and Samsung devices ● SOP-8 (Exposed Pad ) Pb-Free Package ● UL certificate no: 4787022570-2 Applications ● Backup Battery Pack ● Mobile / Tablet Power ● Digital Cameras and Bluetooth Accessories ● USB Power Output Ports FP6719□ Package Type SP: SOP-8 (Exposed Pad)

车载充电器方案简介

车载充电器方案简介 常规用于汽车电瓶(轿车12V, 卡车24V)供电的车载充电器, 大量使用在各种便携式、手持式设备的充电领域, 诸如: 手机, PDA, GPS等; 车充既要考虑锂电池充电的实际需求（恒压CV，恒流CC，过压保护OVP），又要兼顾车载电瓶的恶劣环境（瞬态尖峰电压，系统开关噪声干扰，EMI等）；因此车充方案选取的IC必须同时满足：耐高压，高效率，高可靠性，低频率（有利于EMI的设计）的芯片；通俗讲就是要求“皮实”。 常见的车充方案简介如下： [1] 单片34063实现的低端车充方案示意图 优点:：低成本； 缺点：(1) 可靠性差，功能单一；没有过温度保护，短路保护等安全性措施； (2) 输出虽然是直流电压，但控制输出恒流充电电流的方式为最大开关电流峰值限制，精度不够高； (3) 由于34063为1.5A开关电流PWM+PFM模式（内部没有误差），其车充方案输出直流电压电流的纹波比较大，不够纯净；输出电流能力也非常有限；（常见于 300ma~600ma之间的低端车充方案中） [2] 34063+NPN（NMOS）实现扩流的车充方案示意图

优点：在[1]方案的基础上扩流来满足不断增长的充电电流能力的需求； 缺点：同样存在[1]方案中类似的不足； [3] 用2576+358+稳压管的方案示意图 优点：(1) 由于2576内置过流保护、过温度保护等安全措施，结合358（双运放）来实现输出恒压CV，恒流CC，过压保护OVP等功能；实现了可靠、安全、完善的锂电池充电方案； (2) 由于2576为固定52K PWM变换器，使得车充的EMI设计相对容易； (3) 由于2576和358均为40V高压双极工艺制造，更加“皮实”； (4) 这种方案常用在0.8A ~ 1.5A左右的车充中； 缺点：(1) 系统相对复杂，成本较高； (2) 恒流CC和过压保护OVP是通过358的输出去控制2576的EN来实现的，因此充电电流有比较大的纹波，CC和OVP的响应速度也不够快（是通过切换2576是否工作来实现的）； [4] XLSEMI设计单片车充IC XL4002示意图

5V3A过认证车充方案IC

一、概述 CX8519是一款降压型PWM转换器，典型输出驱动电流为3.5A无需外加晶体管。设计允许它可在8V～40V的宽输入电压下工作。通过将COMP/EN脚逻辑电平拉低来控制外部关断功能，使其进入待机模式。外部补偿使反馈控制具有良好的线性调整率和负载调整率，具有灵活的外围设计。 CX8519的特点之一是具有可编程的CV/CC模式控制功能。CV（恒压）模式提供了一个稳定的输出电压，CC（恒流）模式提供了一个限流功能。在电流检测放大器输入期间，CC电流值通过外部电阻设定。 CX8519适用于需要用到电流限制功能的DC/DC开关电源上。该器件采用ESOP-8L封装，且工作时只需要很少的外围器件。 二、特性 ●电压输入范围：8V～40V ●线电压Vout（Vref=1.2V）精度为±1% ●CC/CV模式控制（恒流和恒压） ●限流精度为±5% ●输出短路保护 ●过压保护（超出输出电压的118%） ●过温保护 ●内置软启动，启动时间12ms ●固定频率120kHz ●UVLO保护 ●占空比范围（0～90%） ●单独的引脚进行外部补偿和关断控制 ●集成N-MOSFET ●ESOP-8L封装

三、应用 ●车充 ●便携式充电设备 ●高亮度照明设备 ●具有限流功能的多功能DC/DC变换器 四、极限参数 注意：如果器件工作条件超出上述各项极限值，可能对器件造成永久性损坏。上述参数仅仅是工作条件的极限值，不建议器件工作在推荐条件以外的情况。器件长时间工作在极限工作条件下，其可靠性及寿命可能受到影响。

五、功能框图 图1.内部框图

六、管脚定义 VCC LX BST ISEN-ISEN+ COMP/EN FB 图2.管脚结构

CX918 车充芯片车充方案

PULSE-WIDTH-MODULATION BATTERY CHARGER GENERAL DESCRIPTION The CX918 is a constant current, constant voltage power supply controller, which incorporate a voltage mode, a current mode circuit, and pulse width modulation (PWM) switching regulator control circuit. An external sense resistor will set the charge current with ±8% accuracy. An internal resistor divider and precision reference set the final float voltage to 5V with ±2% accuracy. With a 100 KHz switching frequency, the CX918provides a simple solution to the EMI problem. High efficiency up to 90% will minish application component heat. The CX918 also has over-voltage protect, over-thermal protect, and short circuit protect function. At the beginning of the charge, the over-current circuit will limit the charge current not too high. The CX918 is available in a 6-pin SOT 23-6 package. FEATURES z Wide Input Supply Range: 10V to 40V z High Efficiency Current Mode PWM Controller with 100KHz Switching Frequency z ±2% Charge Voltage Accuracy z Constant Switching Frequency for Minimum Noise z ±8% Charge Current Accuracy z Cable compensation function z Automatic Battery Recharge z Automatic Shutdown When Input Supply is Removed z Available in a 6-pin SOT23-6 package APPLICATIONS z SMPS z Charger z Portable Computers z Handheld Instruments TYPICAL APPLICATION Figure 1.FOR 5V/3A CX918